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EL5367
Data Sheet November 9, 2004 FN7457.1
1GHz Triple Current Feedback Amplifier
The EL5367 triple amplifier is of the current feedback variety and exhibits a very high bandwidth of 1GHz at AV = +1 and 800MHz at AV = +2. This makes this amplifier ideal for today's high speed video and monitor applications, as well as a number of RF and IF frequency designs. With a total supply current of just 25mA and the ability to run from a single supply voltage from 5V to 12V, this amplifier offers very high performance for little power consumption. The EL5367 is available in a 16-pin QSOP package and is specified for operation over the full -40C to +85C temperature range.
Features
* Gain-of-1 bandwidth = 1GHz * Gain-of-2 bandwidth = 800MHz * 6000V/s slew rate * Single and dual supply operation from 5V to 12V * Low noise = 1.7nV/Hz * 8.5mA supply current
Applications
* Video amplifiers * Cable drivers * RGB amplifiers
Pinout
EL5367 (16-PIN QSOP) TOP VIEW
INMA 1 VSMA 2 INPA 3 VSMB 4 GND 5 INPB 6 VSMC 7 INPC 8 16 VSPA 15 OUTA 14 INMB 13 VSPB 12 OUTB 11 INMC 10 VSPC 9 OUTC
* Test equipment * Instrumentation * Current-to-voltage converters
Ordering Information
PART NUMBER EL5367IU EL5367IU-T7 EL5367IU-T13 PACKAGE 16-Pin QSOP 16-Pin QSOP 16-Pin QSOP TAPE & REEL 7" 13" PKG. DWG. # MDP0040 MDP0040 MDP0040
1
CAUTION: These devices are sensitive to electrostatic discharge; follow proper IC Handling Procedures. 1-888-INTERSIL or 321-724-7143 | Intersil (and design) is a registered trademark of Intersil Americas Inc. Copyright (c) Intersil Americas Inc. 2002-2004. All Rights Reserved. Elantec is a registered trademark of Elantec Semiconductor, Inc. All other trademarks mentioned are the property of their respective owners.
EL5367
Absolute Maximum Ratings (TA = 25C)
Supply Voltage between VS+ and VS- . . . . . . . . . . . . . . . . . . . 13.2V Maximum Continuous Output Current . . . . . . . . . . . . . . . . . . . 50mA IOUT . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 200mA I into VIN+, VIN- . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 4mA Power Dissipation . . . . . . . . . . . . . . . . . . . . . . . . . . . . . See Curves Pin Voltages. . . . . . . . . . . . . . . . . . . . . . . . . VS- -0.5V to VS+ +0.5V Storage Temperature . . . . . . . . . . . . . . . . . . . . . . . .-65C to +150C Ambient Operating Temperature . . . . . . . . . . . . . . . .-40C to +85C Die Junction Temperature . . . . . . . . . . . . . . . . . . . . . . . . . . . +125C
CAUTION: Stresses above those listed in "Absolute Maximum Ratings" may cause permanent damage to the device. This is a stress only rating and operation of the device at these or any other conditions above those indicated in the operational sections of this specification is not implied. IMPORTANT NOTE: All parameters having Min/Max specifications are guaranteed. Typical values are for information purposes only. Unless otherwise noted, all tests are at the specified temperature and are pulsed tests, therefore: TJ = TC = TA
Electrical Specifications
PARAMETER AC PERFORMANCE BW
VS+ = +5V, VS- = -5V, RF = 392 for AV = 1, RF = 250 for AV = 2, RL = 150, TA = 25C, unless otherwise specified. CONDITIONS MIN TYP MAX UNIT
DESCRIPTION
-3dB Bandwidth (per channel)
AV = +1 AV = +2
1000 800 100 3000 6000 8 1.7 19 50 0.01 0.03
MHz MHz MHz V/s ns nV/Hz pA/Hz pA/Hz %
BW1 SR tS eN iNiN+ dG dP
0.1dB Bandwidth (per channel) Slew Rate 0.1% Settling Time Input Voltage Noise IN- Input Current Noise IN+ Input Current Noise Differential Gain Error (Note 1) Differential Phase Error (Note 1)
AV = +2 VO = -2.5V to +2.5V, AV = +2 VOUT = -2.5V to +2.5V, AV = -1
DC PERFORMANCE VOS TCVOS ROL Offset Voltage Input Offset Voltage Temperature Coefficient Transimpedance Measured from TMIN to TMAX 0.5 -5 -0.5 3.52 1.1 2.5 5 mV V/C M
INPUT CHARACTERISTICS CMIR CMRR -ICMR +IIN -IIN RIN CIN Common Mode Input Range (guaranteed by CMRR test) Common Mode Rejection Ratio - Input Current Common Mode Rejection + Input Current - Input Current Input Resistance Input Capacitance 3 52 0 -25 -25 50 3.3 57 0.7 0.7 8.5 130 1.5 66 1 25 25 250 V dB A/V A A k pF
OUTPUT CHARACTERISTICS VO Output Voltage Swing RL = 150 to GND RL = 1k to GND IOUT Output Current RL = 10 to GND 3.6 3.8 110 3.8 4.0 160 4.1 4.2 200 V V mA
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FN7457.1 November 9, 2004
EL5367
Electrical Specifications
PARAMETER SUPPLY IS PSRR -IPSR NOTE: 1. Standard NTSC test, AC signal amplitude = 286mV, f = 3.58MHz. Supply Current - Enabled Power Supply Rejection Ratio - Input Current Power Supply Rejection No load, VIN = 0V DC, VS = 4.75V to 5.25V DC, VS = 4.75V to 5.25V 7.5 70 -0.5 8.5 50 0.2 1 9.3 mA dB A/V VS+ = +5V, VS- = -5V, RF = 392 for AV = 1, RF = 250 for AV = 2, RL = 150, TA = 25C, unless otherwise specified. (Continued) CONDITIONS MIN TYP MAX UNIT
DESCRIPTION
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FN7457.1 November 9, 2004
EL5367 Typical Performance Curves
5 NORMALIZED MAGNITUDE (dB) VCC=5V VEE=-5V 3 RL=150 4 RF=368 NORMALIZED MAGNITUDE (dB) VCC=5V VEE=-5V 2 RL=150 RF=392 0
RF=392 RF=662 RF=511 RF=608 RF=698
RG=186 RG=392
1
-1
-2 RG=93 RG=43 -6 100K 1M 10M FREQUENCY (Hz) 100M 1G
-3
RF=806 RF=900 1M 10M FREQUENCY (Hz) RF=1K 1G
-4
-5 100K
100M
FIGURE 1. FREQUENCY RESPONSE AS THE FUNCTION OF RF
5 NORMALIZED MAGNITUDE (dB)
FIGURE 2. FREQUENCY RESPONSE AS THE FUNCTION OF THE GAIN
5 NORMALIZED MAGNITUDE (dB)
VCC=+5V VEE=-5V 3 RL=150 RF=392 1
C=4.7pF C=2.5pF
VCC=+5V VEE=-5V 3 RL=150 RF=RG=392 1
C=4.7pF C=2.5pF
-1
C=1.5pF C=1pF
-1
C=1.5pF C=1pF
-3
C=0pF
-3 C=0pF -5 100K 1M 10M 100M 1G
-5
100K
1M
10M
100M
1G
FREQUENCY (Hz)
FREQUENCY (Hz)
FIGURE 3. FREQENCY RESPONSE vs CIN
FIGURE 4. NON-INVERTING FREQUENCY RESPONSE FOR VARIOUS CIN-
4 NORMALIZED MAGNITUDE (dB)
VCC, VEE=5V RF=220 RG=220
2
VCC=+5V VEE=-5V RL=150 RF=392
0 RF=220 RG=100 0.5V/DIV
-2
-4
-6 1M
10M
100M
1G
2ns/DIV
FREQUENCY (Hz)
FIGURE 5. INVERTING FREQUENCY RESPONSE FOR GAIN OF 1 AND 2
FIGURE 6. RISE AND FALL TIME
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EL5367 Typical Performance Curves (Continued)
4 NORMALIZED MAGNITUDE (dB) RL=150 RF=300 2 RG=300 5.0V 0 2.5V 3.0V -4 6.0V 4 NORMALIZED MAGNITUDE (dB) RL=150 RF=220 2 RG=220
3.5V
2.5V
0 5.0V -2 6.0V
-2
-4
-6
100K
1M
10M
100M
1G
-6 1M
10M
100M
1G
FREQUENCY (Hz)
FREQUENCY (Hz)
FIGURE 7. FREQUENCY RESPONSE AS THE FUNCTION OF THE POWER SUPPLY VOLTAGE
FIGURE 8. INVERTING AMPLIFIER, FREQUENCY RESPONSE AS THE FUNCTION OF VCC, VEE GAIN - 1
1M 100K ROL ()
ROL
-45 PHASE () -135
OUTPUT IMPDEANCE ()
2.5V 5.0V 6.0V
VCC, VEE=2.5V
45 10
VCC, VEE=5V GAIN=2
10K 2.5V 5.0V 1K PHASE 100 100K 1M 10M 100M 1G
1
-225 -315
100m
10m 10K 100K 1M FREQUENCY (Hz) 10M 100M
FREQUENCY (Hz)
FIGURE 9. TRANSIMPEDANCE MAGNITUDE AND PHASE AS THE FUNCTION OF THE FREQUENCY
0
FIGURE 10. CLOSED LOOP OUTPUT IMPEDANCE vs FREQUENCY
0
PSRR (VCC) (dB)
40 50 60 70 80 100 1K 10K 100K 1M 10M 100M
PSRR (VEE) (dB)
VCC=5V 10 VEE=-5V RL=150 20 RF=402 RG=402 30
VCC=5V 10 VEE=-5V RL=150 20 RF=402 RG=402 30 40 50 60 70 80 100 1K 10K 100K 1M 10M 100M
FREQUENCY (Hz)
FREQUENCY (Hz)
FIGURE 11. PSRR +5V
FIGURE 12. PSRR -5V
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FN7457.1 November 9, 2004
EL5367 Typical Performance Curves (Continued)
20 10 0 -10 CMRR (dB) -20 -30 -40 -50 -60 -70 -80 3.5V 1K 10K 100K 1M 5.0V 10M 100M 2.5V 6.0V RF=RG=392 3 NORMALIZED MAGNITUDE (dB)
1
-1
-3 V =5V CC VEE=-5V RL=150 -5 GAIN=2 LOAD=150 INPUT LEVEL=3VP-P -7 100K 1M 10M
100M
1G
FREQUENCY (Hz)
FREQUENCY (Hz)
FIGURE 13. COMMON MODE REJECTION AS THE FUNCTION OF THE FREQUENCY AND POWER SUPPLY VOLTAGE
2
FIGURE 14. LARGE SIGNAL RESPONSE
-50
DISTORTION (dB)
1.5 VOUTP-P (V) 3.0V 1 2.5V 0.5
6.0V
VCC, VEE=5V -55 RL=150 AV=2 -60 -65 -70 -75 -80 2ND HD 3RD HD THD
5.0V
0 100 200 300 400 500 600 700 800 900 FREQUENCY (Hz)
1K
-85
1
6
11
16
21
26
31
36
FREQUENCY (MHz)
FIGURE 15. TOUT vs FREQUENCY AND VCC, VEE
-74 -76 DISTORTION (dB) -78 -80 -82 -84 -86 3RD HD 2ND HD THD
FIGURE 16. DISTORTION vs FREQUENCY
10
VCC, VEE=5V RL=150 AV=2 DISTORTION (dB)
f=5MHz RL=150 -10 AV=2 VO=2VP-P -30
-50 THD 3RD HD 5 6 2ND HD 7 8 9 10 11 12
-70
5
6
7
8
9
10
11
12
-90
TOTAL SUPPLY VOLTAGE (V)
TOTAL SUPPLY VOLTAGE (V)
FIGURE 17. HARMONIC DISTORTION vs SUPPLY VOLTAGE
FIGURE 18. HARMONIC DISTORTION vs SUPPLY VOLTAGE
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FN7457.1 November 9, 2004
EL5367 Typical Performance Curves (Continued)
f=10MHz RL=150 AV=2 -60 VO=2VP-P THD -70 2ND HD 3RD HD -50 f=20MHz RL=150 -55 A =2 V VO=2VP-P -60 -65 -70 -75 -90 -80 -50
DISTORTION (dB)
DISTORTION (dB)
THD 2ND HD 3RD HD 5 6 7 8 9 10 11 12
-80
5
6
7
8
9
10
11
12
TOTAL SUPPLY VOLTAGE (V)
TOTAL SUPPLY VOLTAGE (V)
FIGURE 19. DISTORTION vs POWER SUPPLY VOLTAGE
FIGURE 20. DISTORTION vs POWER SUPPLY VOLTAGE
8.5 8.4 SUPPLY CURRENT (mA) 8.2 8.1 8 7.9 7.8 7.7 7.6 7.5 7.4 2.5 3 3.5 4 4.5 5 5.5 6 ISIS+ POWER DISSIPATION (W) 8.3
1.4 1.2
JEDEC JESD51-7 HIGH EFFECTIVE THERMAL CONDUCTIVITY TEST BOARD
1 893mW 0.8 0.6 0.4 0.2 0 0 25 50 75 85 100 125 150
JA
QS O = 1 P1 6 12 C /W
SUPPLY VOLTAGE (V)
AMBIENT TEMPERATURE (C)
FIGURE 21. SUPPLY CURRENT vs SUPPLY VOLTAGE
FIGURE 22. PACKAGE POWER DISSIPATION vs AMBIENT TEMPERATURE
1.2 POWER DISSIPATION (W) 1 0.8
LOW EFFECTIVE THERMAL CONDUCTIVITY TEST BOARD
633mW 0.6 0.4 0.2 0
J QS
A =1
58
OP
16 C /W
0
25
50
75 85 100
125
150
AMBIENT TEMPERATURE (C)
FIGURE 23. PACKAGE POWER DISSIPATION vs AMBIENT TEMPERATURE
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FN7457.1 November 9, 2004
EL5367 Pin Descriptions
16-PIN QSOP 3 6 8 1 14 11 2 4 7 16 13 10 15 12 9 PIN NAME INPA INPB INPC INMA INMB INMC VSMA VSMB VSMC VSPA VSPB VSPC OUTA OUTB OUTC FUNCTION Non-inverting input Non-inverting input Non-inverting input Inverting Inverting Inverting Negative supply Negative supply Negative supply Positive supply Positive supply Positive supply Output Output Output
For good AC performance, parasitic capacitance should be kept to a minimum, especially at the inverting input. (See the Capacitance at the Inverting Input section) Even when ground plane construction is used, it should be removed from the area near the inverting input to minimize any stray capacitance at that node. Carbon or Metal-Film resistors are acceptable with the Metal-Film resistors giving slightly less peaking and bandwidth because of additional series inductance. Use of sockets, particularly for the SO package, should be avoided if possible. Sockets add parasitic inductance and capacitance which will result in additional peaking and overshoot.
Capacitance at the Inverting Input
Any manufacturer's high-speed voltage- or current-feedback amplifier can be affected by stray capacitance at the inverting input. For inverting gains, this parasitic capacitance has little effect because the inverting input is a virtual ground. But for non-inverting gains, this capacitance (in conjunction with the feedback and gain resistors) creates a pole in the feedback path of the amplifier. This pole, if low enough in frequency, has the same destabilizing effect as a zero in the forward open-loop response. The use of large value feedback and gain resistors exacerbates the problem by further lowering the pole frequency (increasing the possibility of oscillation). The EL5367 frequency response is optimized with the resistor values in Figure 3. With the high bandwidth of this amplifier, these resistor values might cause stability problems when combined with parasitic capacitance, thus ground plane is not recommended around the inverting input pin of the amplifier.
Applications Information
Product Description
The EL5367 is a current-feedback operational amplifier that offers a wide -3dB bandwidth of 1GHz and a low supply current of 8.5mA per amplifier. The EL5367 works with supply voltages ranging from a single 5V to 10V and it is also capable of swinging to within 1V of either supply on the output. Because of their current-feedback topology, the EL5367 does not have the normal gain-bandwidth product associated with voltage-feedback operational amplifiers. Instead, its -3dB bandwidth remains relatively constant as closed-loop gain is increased. This combination of high bandwidth and low power, together with aggressive pricing make the EL5367 an ideal choice for many low-power/highbandwidth applications such as portable, handheld, or battery-powered equipment.
Feedback Resistor Values
The EL5367 has been designed and specified at a gain of +2 with RF approximately 392. This value of feedback resistor gives 800MHz of -3dB bandwidth at AV = 2 with about 0.5dB of peaking. Since the EL5367 is current-feedback amplifier, it is also possible to change the value of RF to get more bandwidth. As seen in the curve of Frequency Response for Various RF and RG, bandwidth and peaking can be easily modified by varying the value of the feedback resistor. Because the EL5367 is a current-feedback amplifier, its gain-bandwidth product is not a constant for different closedloop gains. This feature actually allows the EL5367 to maintain reasonable constant -3dB bandwidth for different gains. As gain is increased, bandwidth decreases slightly while stability increases. Since the loop stability is improving with higher closed-loop gains, it becomes possible to reduce the value of RF below the specified 250 and still retain stability, resulting in only a slight loss of bandwidth with increased closed-loop gain.
Power Supply Bypassing and Printed Circuit Board Layout
As with any high frequency device, good printed circuit board layout is necessary for optimum performance. Low impedance ground plane construction is essential. Surface mount components are recommended, but if leaded components are used, lead lengths should be as short as possible. The power supply pins must be well bypassed to reduce the risk of oscillation. The combination of a 4.7F tantalum capacitor in parallel with a 0.01F capacitor has been shown to work well when placed at each supply pin.
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FN7457.1 November 9, 2004
EL5367
Supply Voltage Range and Single-Supply Operation
The EL5367 has been designed to operate with supply voltages having a span of greater than 5V and less than 10V. In practical terms, this means that the EL5367 will operate on dual supplies ranging from 2.5V to 5V. With singlesupply, they will operate from 5V to 10V. As supply voltages continue to decrease, it becomes necessary to provide input and output voltage ranges that can get as close as possible to the supply voltages. The EL5367 has an input range which extends to within 1.8V of either supply. So, for example, on 5V supplies, the EL5367 has an input range which spans 3.2V. The output range of the EL5367 is also quite large, extending to within 1V of the supply rail. On a 5V supply, the output is therefore capable of swinging from -4V to +4V.
Current Limiting
The EL5367 has no internal current-limiting circuitry. If the output is shorted, it is possible to exceed the Absolute Maximum Rating for output current or power dissipation, potentially resulting in the destruction of the device.
Power Dissipation
With the high output drive capability of the EL5367, it is possible to exceed the 125C Absolute Maximum junction temperature under certain very high load current conditions. Generally speaking when RL falls below about 25, it is important to calculate the maximum junction temperature (TJMAX) for the application to determine if power supply voltages, load conditions, or package type need to be modified for the EL5367 to remain in the safe operating area. These parameters are calculated as follows:
T JMAX = T MAX + ( JA x n x PD MAX )
Video Performance
For good video performance, an amplifier is required to maintain the same output impedance and the same frequency response as DC levels are changed at the output. This is especially difficult when driving a standard video load of 150, because of the change in output current with DC level. Previously, good differential gain could only be achieved by running high idle currents through the output transistors (to reduce variations in output impedance.) These currents were typically comparable to the entire 8.5mA supply current of each EL5367 amplifier. Special circuitry has been incorporated in the EL5367 to reduce the variation of output impedance with current output. This results in dG and dP specifications of 0.01% and 0.03, while driving 150 at a gain of 2.
where: TMAX = Maximum ambient temperature JA = Thermal resistance of the package n = Number of amplifiers in the package PDMAX = Maximum power dissipation of each amplifier in the package PDMAX for each amplifier can be calculated as follows:
V OUTMAX PD MAX = ( 2 x V S x I SMAX ) + ( V S - V OUTMAX ) x --------------------------R
L
where: VS = Supply voltage ISMAX = Maximum supply current of 1A VOUTMAX = Maximum output voltage (required) RL = Load resistance
Output Drive Capability
In spite of the low 8.5mA of supply current, the EL5367 is capable of providing a minimum of 110mA of output current. With so much output drive, the EL5367 is capable of driving 50 loads to both rails, making it an excellent choice for driving isolation transformers in telecommunications applications.
Driving Cables and Capacitive Loads
When used as a cable driver, double termination is always recommended for reflection-free performance. For those applications, the back-termination series resistor will decouple the EL5367 from the cable and allow extensive capacitive drive. However, other applications may have high capacitive loads without a back-termination resistor. In these applications, a small series resistor (usually between 5 and 50) can be placed in series with the output to eliminate most peaking. The gain resistor (RG) can then be chosen to make up for any gain loss which may be created by this additional resistor at the output. In many cases it is also possible to simply increase the value of the feedback resistor (RF) to reduce the peaking.
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FN7457.1 November 9, 2004
EL5367 Typical Application Circuits
0.1F +5V IN+ INVS+ 1/3 OUT EL5367 VS0.1F 5 250 +5V IN+ INVS+ 1/3 OUT EL5367 VS0.1F 250 250 0.1F
-5V 250 -5V
0.1F +5V IN+ INVS+ 1/3 OUT EL5367 VS0.1F 5
0.1F VOUT 250 VIN +5V IN+ INVS+ 1/3 OUT EL5367 VS0.1F
VOUT
-5V VIN 250 250
-5V
FIGURE 24. INVERTING 200mA OUTPUT CURRENT DISTRIBUTION AMPLIFIER
FIGURE 25. FAST-SETTLING PRECISION AMPLIFIER
0.1F +5V IN+ INVS+ 1/3 OUT EL5367 VS0.1F 120 0.1F +5V IN+ INVS+ 1/3 OUT EL5367 VS0.1F 120 240 0.1F VOUT1k +5V IN+ IN0.1F VOUT+ 1k -5V 250 250 +5V IN+ IN-
0.1F
VS+ 1/3 OUT EL5367 VS0.1F
-5V 250
0.1F
VS+ 1/3 OUT EL5367 VS0.1F
VOUT
-5V VIN 250 250 -5V 250
250 RECEIVER
TRANSMITTER
FIGURE 26. DIFFERENTIAL LINE DRIVER/RECEIVER
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FN7457.1 November 9, 2004
EL5367 Package Outline Drawing
NOTE: The package drawing shown here may not be the latest version. To check the latest revision, please refer to the Intersil website at
All Intersil U.S. products are manufactured, assembled and tested utilizing ISO9000 quality systems. Intersil Corporation's quality certifications can be viewed at www.intersil.com/design/quality
Intersil products are sold by description only. Intersil Corporation reserves the right to make changes in circuit design, software and/or specifications at any time without notice. Accordingly, the reader is cautioned to verify that data sheets are current before placing orders. Information furnished by Intersil is believed to be accurate and reliable. However, no responsibility is assumed by Intersil or its subsidiaries for its use; nor for any infringements of patents or other rights of third parties which may result from its use. No license is granted by implication or otherwise under any patent or patent rights of Intersil or its subsidiaries.
For information regarding Intersil Corporation and its products, see www.intersil.com 11
FN7457.1 November 9, 2004

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